
made with the wide-band RF system of the PS. This new
requirement means that RF systems in PS and SPS that
were previously operated stand-alone must be synchronised.
The beam energy has to be temporarily changed in the PS
to overlap the position of the longitudinal gap with the rise
time of the PS extraction kickers. This can only be done with
enough voltage available in the main RF system, especially
if the manipulation is to be performed on the order of ten
milliseconds.
Due to the low RF voltage requirements of the transverse
beam splitting,
𝑉RF
must be lowered well before the end
of the cycle. The Finemet system can only generate a low
RF voltage, too small to synchronise the beam. Hence the
synchronisation is proposed to take place at the beginning of
the magnetic flat-top, where the RF voltage is still sufficient
to re-phase the beam quickly. Due to the periodicity it only
requires at maximum a half of a
ℎ=16
bucket phase change
in either direction. This is also required because the barrier-
bucket transfer from
ℎ=16
is non-adiabatic, which means
that the barrier is most effective once the voltage is already
raised between two existing
ℎ=16
buckets, as shown in
Fig. 8.
The beam phase measurements for
ℎ=16
and then
ℎ=1
have to take place at the same frequency as the SPS. At a
fixed bending field in the PS this means that the mean radial
position at the time of the measurements must be the same as
the one at extraction. This poses a problem for the transverse
splitting process as its ideal radial position is centred. Hence,
in open loop, a constant frequency excursion is programmed
to centre the beam for the transverse splitting and then after
the process steer it to the extraction orbit with the RF systems.
This only introduces a fixed, repeatable phase offset that does
not affect the synchronisation.
Since the bunches after the cogging are
ℎ=16
syn-
chronous with the SPS, the final
ℎ=1
synchronisation is
only a bucket selection, which can be pre-calculated. There-
fore, no change in beam energy is needed for the
ℎ=1
part.
The steps of the proposed synchronisation sequence are
summarised in Table 1.
Table 1: Synchronisation sequence in PS
Cycle time [ms] Action
590-600 Loops off, ℎ=16 phase measurement
600 ℎ=1phase measurement
600-620 Cogging
620-650 Radial steering to central orbit
650-770 Constant offset for MTE
770-800 Radial steering to extraction orbit
800-815 Hand-over ℎ=16 to barrier bucket
800-815 Debunching
835 Extraction
Cogging
The principle of phase correction at a fixed magnetic
field,
𝐵
is to change the frequency of the beam such that the
integral of the frequency change equals the desired phase
difference. This requires a phase measurement at the refer-
ence frequency, a phase correction, and then returning to
the original frequency, thus implying that the beam has to
be accelerated and then decelerated.
Since the bending field is constant, the beam is also radi-
ally offset according to the relation [24,25]:
𝑑𝑓
𝑓
=
𝛾2
𝛾2
tr −𝛾2
𝑑𝑅
𝑅,(1)
where
𝑓
is the beam revolution frequency,
𝑅
the PS radius,
𝛾
the Lorentz factor, and
𝛾tr
the gamma at transition. The
frequency offset needs to be small enough due to aperture
limitation. Longitudinal macro-particle tracking simulations
have been performed to validate the phase curve [26]
𝜙(𝜙set, 𝑇, 𝑡)=
𝜙set
𝑇𝑡−𝑇
2𝜋sin 2𝜋
𝑇𝑡 (2)
𝑡∈ [0, 𝑇];𝜙set ∈ [−2𝜋, 2𝜋],(3)
which corresponds to the programmed frequency curve of
𝑓(𝜙set, 𝑇, 𝑡)=
𝜙set
2𝜋𝑇 1−cos 2𝜋
𝑇𝑡 .(4)
It defines the set of frequency curves for the
ℎ=16
correc-
tion, which can be seen in Fig. 7 (middle). Note that the
phase range is set conservatively for a whole bucket move-
ment in either direction, which is useful for testing - half of
this phase change is sufficient in operation.
IMPLEMENTATION
Synchronisation can be tried with the current PS beam
control system if one acts on the master direct digital synthe-
sizer (DDS) frequency as depicted in Fig. 2. Phase slips and
frequency steering can be implemented for all RF systems in-
volved in the synchronisation simultaneously since the mas-
ter clock frequency drives the clock signal for the low-level
RF (LLRF) cavity controllers. Since this is an open-loop ma-
nipulation, the handover from closed-loop (see long latency
loops in Fig. 2) to open-loop has to be implemented. In
order to significantly reduce phase drift during flat-top, the
precision of the frequency word has to be increased from 23
bits to 32 bits in open loop.
To reduce development time and cost, a rapid proto-
typing solution was chosen, also taking into account the
challenge of electronic component availability. A custom
board was designed to interface an ARM
r
Cortex
r
M7 con-
troller (STM32H723ZG) on a development board with the
current beam control (see Fig. 3). The controller’s digital
interface is compatible with the LVTTL/TTL signals of the
frequency distribution [28]. Hence, adding only a thin layer
of power management and IO interface was sufficient. The